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TK83361M
NARROW BAND FM IF IC FEATURES
n Wide Operating Voltage Range 2.0 to 8.0V n RF Input Frequency up to 220 MHz n Low Supply Current (2.8mA, squelch off, 3.8mA, n n
squelch on) Low External Component Count Excellent Limiting Sensitivity (-3dB = 8dB)
APPLICATIONS
n n n n n
Amateur Radio Transceivers Cordless Phones Remote Controls Wireless Data Transceivers Battery Powered Devices
DESCRIPTION
The TK83361M is a narrow band FM IF IC designed for cordless phones, radio transceivers, remote controls, wireless data transceivers, and other communication equipment. It integrates the mixer, oscillator, limiting amplifier, FM demodulator, filter amplifier and squelch circuit into a single surface mount SOP-16 package. The low operating current combined with a minimum operating voltage of only 2 V makes this device ideal for battery powered devices. The TK83361M offers improved performance over the MC3361C. The operating frequency has been increased to 220MHz (vs. 60MHz) while reducing the supply current from 5.2 mA to 3.8mA (squelch on). Offered in the SOP-16 surface mount package, the TK83361M is a drop-in replacement for the MC3361C.
TK83361M
OSC (B) 1 16 RF INPUT
OSC (E) 2
15 GND
MIXER OUT 3
14 SCAN CONTROL
VCC
4
13 SCAN CONTROL
IF INPUT
5
12 SQUELCH INPUT 11 FILTER AMP OUTPUT 10 FILTER AMP INPUT 9 AF OUTPUT
DECOUPLE
6
DECOUPLE
7
QUAD COIL
8
BLOCK DIAGRAM
ORDERING INFORMATION
OSC (B) 1
OSC
MIXER
16 RF INPUT
TK83361M
Tape/Reel Code
OSC (E) 2
GND
15 GND
MIXER OUT 3
SQUELCH
14 SCAN CONTROL
VCC
4
VCC
13 SCAN CONTROL
TAPE/REEL CODE
TL: Tape Left
IF INPUT
5
12 SQUELCH INPUT 11 FILTER AMP OUTPUT 10 FILTER AMP INPUT
10pF QUAL DET
DECOUPLE
6
LIMIT AMP
FILTER AMP
DECOUPLE
7
QUAD COIL
8
9 AF OUTPUT
December 2000 TOKO, Inc.
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TK83361M
ABSOLUTE MAXIMUM RATINGS
Supply Voltage ........................................................ 10 V Operating Voltage ......................................... 2.0 to 8.0 V Power Dissipation (Note 1) ................................ 600 mW Storage Temperature Range ................... -55 to +150 C Operating Temperature Range .................. -30 to +70 C Input Frequency ............................................... 220 MHz
TK83361M ELECTRICAL CHARACTERISTICS
Test Conditions: VCC = 4.0 V, fRF = 10.7 MHz, VRF = +80dB, fm = 1kHz, fdev = 3kHz, fOSC = 10.245MHz, Ta = 25C, unless otherwise specified.
SYMBOL ICC1 ICC2 Limit VO ZO THD GM RIM Gf fOC SH SL SH SL HYS
PARAMETER Supply Current 1 Supply Current 2 -3dB Limiting Sensitivity Output Voltage Output Impedance Total Harmonic Distortion Mixer Conversion Gain Mixer Input Impedance Filter Amplifier Gain Filter Amplifier Output Terminal Voltage Scan Control High Level Scan Control Low Level Scan Control High Level Scan Control Low Level Squelch Hysteresis
TEST CONDITIONS No Signal, Squelch off No Signal, Squelch on -3dB pt.(1kHz) VRF = +80dB, fdev = 3kHz VRF = +80dB, fdev = 3kHz VRF = +80dB, fdev = 3kHz Pin 3: terminated DC Measurement fin = 10kHz, Vin = 0.3mV No Signal Squelch Input VSQ = 0.0V Squelch Input VSQ = 2.5V Squelch Input VSQ = 2.5V Squelch Input VSQ = 0.0V
MIN
TYP 2.8 3.8 8
MAX 3.5 4.9 15
UNITS mA mA dB mVrms
130
170 450 0.86 2.5
% dB k dB
21
28 3.3
40 0.5 3.0
50 0.7 3.9 0.0 0.4 0.9
V V V V
3.0
3.9 0.0 45 0.4 100
V mV
Note 1: Power dissipation must be decreased at a rate of 4.8 mW/C for operation above 25C.
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December 2000 TOKO, Inc.
TK83361M
TEST CIRCUIT
10.245MHz 1 33pF 10F + 0.1F CF
VCC
0.01F MIXER OSC 2 GND 15 50 100k 3 SQUELCH 4 VCC 13 14 10k
VCC
16
120pF
5 0.1F 6 0.1F 7 LIMIT AMP FILTER AMP
12 1F + 11 470k 1F + 510
10 10pF
CF = BLFC455D (TOKO) CFU455D2 (MURATA) QUAD COIL = 7MCS-13546Z
20k 8 QUAD COIL
9 QUAD DET 8.2k 0.01F
TYPICAL PERFORMANCE CHARACTERISTICS
9 - 1. Mixer + IF Section
VO(DET), AMR, N, THD vs.
VO(DET), OUTPUT LEVEL, AMR, AM REJECTION AND N, NOISE (dBV)
VO(DET), AMR, N, THD vs.
VO(DET), Output Level, AMR, AM REJECTION AND N, NOISE (dBV)
-10 -20 -30 -40 -50 -60 -70
RF INPUT SIGNAL LEVEL
VO(DET) V =4.0V cc f =10.7MHz RF f =1kHz, f =3kHz m dev fOSC=10.245MHz AMR(mod=30%)
7.0 6.0 5.0 4.0 3.0 2.0 1.0
THD, TOTAL HARMONIC DISTORTION(%)
-10 -20 -30 -40 -50 -60 -70
RF INPUT SIGNAL LEVEL
VO(DET) V =4.0V cc f =455kHz IF f =1kHz, f =3kHz m dev
7.0 6.0 5.0 4.0 3.0 2.0
N
THD, TOTAL HARMONIC DISTORTION(%)
AMR (MOD.=30%)
THD
N
THD
1.0
-80 0.0 -20 0 +20 +40 +60 +80 +100 +120 VRF, RF INPUT SIGNAL LEVEL (dB)
TRANSIENT RESPONSE
-80 0.0 -20 0 +20 +40 +60 +80 +100 +120 VIF, IF INPUT SIGNAL LEVEL (dB)
20dB NQS vs. RF INPUT FREQUENCY
4.0
SUPPLY VOLTAGE, OUTPUT LEVEL (V)
VCC 1kHz3kHz Non-mod
RELATIVE 20dB NQ SENSITIVITY(dB)
3.5 3.0 2.5 2.0 1.5 1.0 0.5
fRF = 10.7MHz f m = 1kHz fdev = 3kHz fOSC = 10.245MHz VOSC = 0dBm
0 -20 -40 -60 0 -20 -40 -60 -20 -15 -10 -5 0 +5 +10 +15 +20 fRFf RF, RF INPUT FREQUENCY(kHz)
20dB NQS = 18.0dB fRF = 58MHz fOSC = 58.545MHz 20dB NQS = 17.5dB fRF = 10.7MHz fOSC = 10.245MHz
0.0 -0.5 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 R, RISE TIME (msec)
December 2000 TOKO, Inc.
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TK83361M
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
9 - 2. Mixer Section
32
GM, MIXER CONVERSION GAIN (dB)
MIXER INPUT FREQUENCY RESPONSE
30 28
VOMR, RELATIVE MIXER OUTPUT LEVEL (dB)
0 -2 -4 -6 -8 -10 -12 -14 -16 -18 -20
MIXER OUTPUT FREQUENCY RESPONSE
26
VCC = 4.0V fRF VARIABLE VRF = +60dB fOM = 455kHz VOSC = 0dBm
VCC = 4.0V fRF = 10.7MHz VRF = +60dB fOSC VARIABLE VOSC = 0dBm
24 22 1M
10M 100M 1G fRF, RF INPUT FREQUENCY (Hz)
THE 3rd ORDER INTERCEPT POINT
100k 1M 10M fOM, MIXER OUTPUT FREQUENCY (Hz)
SINAD, GM S/N vs. LOCAL OSC INPUT SIGNAL LEVEL
VOM, MIXER OUTPUT LEVEL (dB)
IIP3 = 107dB
SINAD, 12dB SINAD SENSITIVITY (dB) S/N, signal to noise ratio (dB)
140 120 100 80 60
3rd ORDER INTERMOD fRF1 = 10.7125MHz fRF2 = 10.725MHz 1st ORDER DESIRED fRF = 10.7MHz
60
SINAD
35
GM
50 40 30
S/N
30
25 20
fRF = 10.7MHz 21MHz 58MHz 83MHz
GM, MIXER CONVERSION GAIN(dB)
20 10
15 10
40 20
20
40 60 80 100 120 VRF, RF INPUT SIGNAL LEVEL (dB)
9 - 3. IF Section
OUTPUT LEVEL, TOTAL HARMONIC DISTORTION vs. IF INPUT FREQUENCY 10.0 -10 V
O(DET)
0 -70 -60 -50 -40 -30 -20 -10 0 10 20 0 VOSC, LOCAL OSC INPUT SIGNAL LEVEL (dB)
OUTPUT DC VOLTAGE vs. IF INPUT FREQUENCY
VO(DC), OUTPUT DC VOLTAGE (V)
4.0 3.5 3.0 2.5 2.0 1.5 1.0
RD
VO(DET), OUTPUT LEVEL(dBV)
-20 -30 -40 -50
VCC = 4.0V VIF = 80dB f m = 1kHz fdev =3kHz
8.0 6.0
VCC = 4.0V VIF = +80dB
THD, TOTAL HARMONIC DISTORTION(%)
4.0 2.0
THD
VCC
RD = 5k
QUAD COIL
RD = 10k RD = 20k
.5
8
-60 0.0 -40 -30 -20 -10 0 +10 +20 +30 +40 455f IF, IF INPUT FREQUENCY (kHz)
0 -80 -60 -40 -20 0 +20 +40 +60 +80 455f IF, IF INPUT FREQUENCY (kHz)
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TK83361M
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
OUTPUT LEVEL, TOTAL HARMONIC DISTORTION vs. IF DEVIATION FREQUENCY
OUTPUT LEVEL vs. IF MODULATION FREQUENCY
6.0
VO(DET)R, RELATIVE OUTPUT LEVEL (dB)
VO(DET), OUTPUT LEVEL(mVrms)
600 500 400 300 200
VO(DET) VCC =4.0V fIF = 455kHz VIF = +80dB f m = 1kHz
0
RD = 20k
5.0 4.0 3.0 2.0 1.0
THD
THD, TOTAL HARMONIC DISTORTION(%)
10k
-10
5k
-20
VCC
-30 -40
100 0
VCC =4.0V fIF = 455kHz VIF = +80dB fdev = 3kHz Pin 9: open
RD
QUAD COIL
8
0
1 2 3 4 5 6 7 8 9 10 fdev., IF DEVIATION FREQUENCY (kHz)
0.0
100 1k 10k 100k 1M f m , IF MODULATION FREQUENCY (HZ)
INPUT LEVEL RESPONSE 10
Vout , OUTPUT LEVEL(Vrms)
9 - 4. Filter Amplifer Section
GAIN vs. INPUT FREQUENCY
Gf , FILTER AMPLIFIER GAIN (dB)
70 60 50 40 30
1F +
100
THD
VCC = 4.0V Vin = 0.3mV R1 = 510 Rf = 470k
THD, TOTAL HARMONIC DISTORTION(%)
1
VOUT
10.0
20 10 0 1k
11
Rf
100m
1F + 10
R1
VCC = 4.0V Fin = 10kHz R1 = 510 Rf = 470k
1.0
10k
100k
1M
10m 0.1
1
10
0.1 100
fin , FILTER AMPLIFIER INPUT FREQUENCY (Hz)
Vin , INPUT LEVEL(mVrms)
9 - 5. Squelch Section
SCAN CONTROL vs. SQUELCH INPUT VOLTAGE 4.0
SC SC
SC, SC, SCAN CONTROL(V)
3.5 3.0 2.5 2.0 1.5 1.0
VCC = 4.0V
0 .60 .65 .70 .75 .80 VSQ, SQUELCH INPUT VOLTAGE(V)
December 2000 TOKO, Inc.
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TK83361M
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
9 - 6. Versus Supply Voltage Characteristics
SUPPLY CURRENT, 12dB SINAD SENSITIVITY, MIXER CONVERSION GAIN vs. SUPPLY VOLTAGE 9.0 ICC, SUPPLY CURRENT(mA) 8.0 7.0 6.0 5.0 4.0 3.0 2.0 1.0 0.0 1 2 34 5 67 8 VCC, SUPPLY VOLTAGE(V) 9
SINAD ICC1: sq on ICC2: sq off GM
18 16 14 12 10 8 6 4 2 0
36
0
OUTPUT LEVEL, TOTAL HARMONIC DISTORTION, SIGNAL TO NOISE RATIO, OUTPUT DC VOLTAGE vs. SUPPLY VOLTAGE
S/N
SINAD, 12dB SINAD SENSITIVITY(dB)
7 6
70 60
32
28
24 20
16 12 8 4 0
GM, MIXER CONVERSION GAIN(dB)
S/N, SIGNAL TO NOISE RATIO (dB)
VO(DET), OUTPUT LEVEL(dBV)
-5 -10 -15 -20 -25
VO(DET)
THD(%),VO(DC)(V)
5 4
VO(DC)
50 40 30 20 10 0
3 2
THD
-30 -35 1 2 34 5 67 8 VCC, SUPPLY VOLTAGE(V) 9
1 0
MIXER OUTPUT LEVEL vs. SUPPLY VOLTAGE
VTH, VTL , THRESHGf , FILTER OLD VOLTAGE(V) AMP. GAIN(dB)
VOM, MIXER OUTPUT LEVEL(dB)
140 120 100 80 60 40 20 20 40 60 80 100 VRF, RF INPUT SIGNAL LEVEL(dB) 120
VCC = 8.5V 4.0V 2.0V
FILT. AMP. GAIN, FILT. AMP. OUTPUT DC VOLTAGE, THRESHOLD VOLTAGE, HYSTERESIS vs. SUPPLY VOLTAGE 70 1.0 60 50 40 0.8 0.6 0.4 0.2 0.0 1 2 34 5 6 7 8 VCC, SUPPLY VOLTAGE(V) 9
VTH VTL HYS Gf fOC
fOC, OUTPUT DC VOLTAGE HYS, SQUELCH HYSTERESIS(mV)
0.8 0.6 0.4 120 90 60 30 0
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TK83361M
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
9 - 7. Versus Ambient Temperature Characteristics
SUPPLY CURRENT, 12dB SINAD SENSITIVITY, MIXER CONVERSION GAIN vs. AMBIENT TEMPERATURE 9 18
GM
OUTPUT LEVEL, TOTAL HARMONIC DISTORTION, SIGNAL TO NOISE RATIO, OUTPUT DC VOLTAGE vs. AMBIENT TEMPERATURE
SINAD, 12dB SINAD SENSITIVITY(dB)
36 32 28 24 20 16 12 8 4 0
0
7 6
S/N
70 60 50 40 30 20 10 0
GM, MIXER CONVERSION GAIN(dB)
S/N, SIGNAL TO NOISE RATIO (dB)
ICC, SUPPLY CURRENT(mA)
8 7 6 5 4 3 2 1
16 14 12
VO(DET), OUTPUT LEVEL(dBV)
-5 -10 -15 -20 -25 -30 -35
VO(DC) VO(DET)
5 4 3 2 1
THD(%),VO(DC)(V)
SINAD ICC2: sq off
10 8 6
ICC1: sq on
4 2
THD
0 0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE (C)
0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE(C)
MIXER OUTPUT LEVEL vs. AMBIENT TEMPERATURE
VOM, MIXER OUTPUT LEVEL(dB)
140
Gf , FILTER AMP. GAIN(dB)
120 100 80 60 40 20 20 40 60 80 100 VRF, RF INPUT SIGNAL LEVEL(dB) 120
Ta = +25C +85C -40C
70 60 50 40 0.8 0.6 0.4 0.2 0.0
FILT. AMP. GAIN, FILT. AMP. OUTPUT DC VOLTAGE, THRESHOLD VOLTAGE, HYSTERESIS vs. AMBIENT TEMP.
Gf
1.0 0.8 0.6
fOC, OUTPUT DC HYS, SQUELCH VOLTAGE(V) HYSTERESIS(mV)
VTH
fOC
0.5 120
VTH, VTL , THRESHOLD VOLTAGE(V)
VTL
90 60
HYS
30 0
-40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE(C)
December 2000 TOKO, Inc.
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TK83361M
PIN FUNCTION DESCRIPTION
PIN SYMBOL TERMINAL VOLTAGE (V) INTERNAL EQUIVALENT CIRCUIT DESCRIPTION
1
OSC(B)
VCC
The base of the Colpitts oscillator. The Colpitts oscillator is composed of Pin 1 and Pin 2. The emitter of the Colpitts oscillator. Using an external OSC source, local level must be injected into Pin 1, and Pin 2 must be opened. Output of the Mixer.
VCC 4
1
2
OSC(E)
2
3 4
MIXER OUT VCC
Supply Voltage.
3
5
IF INPUT
VCC
Input to the IF limiter amplifier. This pin is terminated by internal 1.8kW resistor.
1.8k 51.8K 50K
5
6 7
DECOUPLE DECOUPLE
IF Decoupling. IF Decoupling
6
7
8
QUAD COIL
10p
VCC
Phase Shifter.
8
9
AF OUTPUT
VCC
Recovered Audio Output
10p 9
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December 2000 TOKO, Inc.
TK83361M
PIN FUNCTION DESCRIPTION (CONT.)
PIN SYMBOL TERMINAL VOLTAGE (V) INTERNAL EQUIVALENT CIRCUIT DESCRIPTION Filter Amplifier Input.
10
FILTER AMPLIFIER INPUT
10
VCC
11
FILTER AMPLIFIER OUTPUT
Filter Amplifier Output.
VCC
11
12
SQUELCH INPUT
Squelch Input.
VCC
13
SCAN CONTROL
12 20k
13
Scan Control.
14
14
SCAN CONTROL
Scan Control.
15 16
GND
VCC 3.3K
Ground Mixer Input.
3.3K 16
RF INPUT
15
December 2000 TOKO, Inc.
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TK83361M
TEST BOARD
Figure 1: Solder Side View (Circuit Side View) Figure 2: Component Placement View
NOTES: 1. Above test board is laid out for the TEST CIRCUIT (page 3). 2. Scale 1:1 (60mmx60mm) 3. 10.245MHz Fundamental mode crystal, about 30pF load. 4. 455kHz CF, TOKO Type BLFC455D or MURATA Type CFU455D2 or equivalent. 5. COIL, TOKO Type 7MCS-13546Z or 7MC-8128Z or equivalent.
APPLICATIONS INFORMATION
12-1. Mixer Section The mixer consists of a Gilbert cell and a local oscillator. The mixer conversion gain, when Pin 4 is terminated, is 28dB. The RF input is unbalanced. 12-1-1. A Local OSC The oscillator included is a general Colpitts type OSC. The drive current of OSC is 200A. Examples of components are shown in Fig. 3. The examples are explained in the next paragraph. Figure 3: Oscillator Components i) Under Crystal Control
VCC
ii) Parallel LC Components
VCC
1
1
2
2
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December 2000 TOKO, Inc.
TK83361M
APPLICATIONS INFORMATION (CONT.)
(1) Using an External Oscillator Source The circuit composition using an external OSC source is shown in Fig. 4. When using an external OSC source instead of the internal OSC, the local level must be injected into Pin 1 by capacitor coupling. In this case, Pin 2 must be open. The local OSC operates as an emitter follower for a multiplier by opening Pin 2 and injecting into Pin 1. Figure 4: External Injection
VCC
tor. It is easy to increase the drive current by connecting resistor Re between Pin 2 and GND. Being short of drive current, it makes gm increase to increase the drive current by connecting external resistor Re. In that case, the amount of drive current increase, Ie, is shown in Eq.(1). V VBE V 0.7 Ie = CC = CC Re Re
(1)
50 ~
0.01 1 50 2 open RF IF
(2) For 3rd Overtone mode In general, a crystal oscillator can oscillate in the fundamental mode and overtone mode. For example, it is easy for a 30MHz-overtone crystal to oscillate at 10MHz, fundamental mode. The reason is because the impedance of the fundamental mode is the same as the impedance of the overtone. Therefore, it is necessary for the circuit to select the overtone frequency by using a tuning coil. How to oscillate a general 3rd overtone oscillator is explained. In the case of an overtone mode of 30MHz and higher, using a crystal oscillator, we recommend the circuit in Fig. 5 to suppress the fundamental mode oscillation. Figure 5: Overtone Mode Circuit
VCC
In order to oscillate at the 3rd overtone frequency, the values of C2, C3 and L (Fig.5) are selected. Fig.6 shows a 2-port impedance response of the C2~C3~L loop network. Regarding the condition of oscillation, the impedance characteristic is capacitive at the vacinity of the overtone frequency. It is reactive at the vicinity of the fundamental frequency. The condition of oscillation is as follows: fOSC is between fa and fb, 3 x fOSC is fb and higher. Please see Fig.6 Figure 6: 2-port Impedance Response of Resonance Network
+j fOSC fa fb
3 X f OSC -j
Where: fa: series resonant freq. fb: parallel resonant freq. fOSC: fundamental mode freq. 3 x fOSC: 3rd order overtone freq.
Equations of 3rd order overtone oscillation are shown below.
Reactance
fa =
1
,
2 LxC2
fb = fa
C 1+ 2 C3
(2)
The series value of the equivalent capacitance at the 3rd 1 order overtone freq. of this network, which is decided in the above -mentioned, and the capacitance of C1 must be equal C1 C2 L 2 to load capacitance CL. C3 Being short of negative resistance of the circuit, increase the transistor's bias current by decreasing Re. It is able to Re decide the OSC level for minute adjusting Re. Please refer the most suitable OSC level range to 12dB SINAD sensitivity versus local OSC input signal level in TYPICAL PERThe following explains how to decide the circuit constants of FORMANCE CHARACTERISTICS. The saturating range the overtone-crystal-oscillation fundamental circuit. is the most suitable OSC level range. It is comparatively As the operating frequency increases the oscillation ampli- easy to decide the circuit constant by examining it with a tude decreases because of a shortage of gm of the oscilla- network analyzer.
X'tal
December 2000 TOKO, Inc.
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TK83361M
APPLICATIONS INFORMATION (CONT.)
12-2. IF Section The IF section includes a 6 stage differential amplifier. The fixed internal input matching resistor is 1.8k. The total gain of the limiting amplifier section is approximately 77dB. The decoupling capacitors of Pin 6~7 must be connected as near as possible to the GND pin of the IC . And, make the impedance of the connecting-to-GND line to be as small as possible. If the impedance is not small enough, the sensitivities may worsen. Figure 7: IF Limiter Amplifier Input Block 12-3-2. Phase Shifter The IF signal from the limiter amplifier is provided with 90 phase shift and drives the quadrature detector. The parallel RCL resonance circuit is capable of using the internal 10pF phase shift capacitor. 12-3-3. Audio Output After quadrature detection, the audio signal is pulled out through Pin 9. The required signal is pulled out through the LPF. 12-3-4. For Stable Operation To prevent worsening the distortion, observe the following notes: (1) Demodulated Output Voltage Too large of a demodulated output voltage will worsen the distortion due to the dynamic range of the demodulator. (2) The Signal Level in Phase Shifter (Pin 8) If the phase shifter signal level is too small, the noise level grows worse. This will cause the distortion to grow worse. (3) Band Width of Phase Shifter (Pin 8) If the bandwidth of the phase shifter is narrower than IF bandwidth, including the demodulated element, the distortion will grow worse. 12-4. Filter Amplifier Section An inverting op amp has an output at Pin 11 and the inverting input at Pin 10. The op amp, which has a wide stable operating temperature range, may be used as an active noise filter. 12-4-1. Active BPF Application An active BPF application is shown in Fig. 9, and its Response is shown in Fig. 10. Note at this point to add the bias voltage at Pin 8 from external source. The signal from the phase shifter is put into the multiplier cell through the emitter follower of transistor Q1. Pin 8 is singleconnected with the base terminal. And, it is necessary for Pin 8 to add the same voltage, as the base terminal of Q2 of the opposite side of Q1 through the multiplier is connected with the supply voltage. If the base voltages differ between transistors Q1 and Q2, it alters the DC zero point or worsens the distortion of the demodulation output.
50K 5 1.8k 51.8K 6
7
12-3. FM Demodulator A quadrature FM demodulator using a Gilbert cell is included. 12-3-1. Internal Equivalent Circuit The internal equivalent circuit is shown in Fig. 8. Figure 8: Internal Equivalent Circuit of Demodulator
VCC QUAD COIL
RD
8
VCC
Active Load
VCC
Q1
Q2
from IF LIM AMP
10pF
Multiplier Cell
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TK83361M
APPLICATIONS INFORMATION (CONT.)
Figure 9. Active BPF VTH indicates the Hi threshold voltage, VTL indicates the Lo threshold voltage in Fig. 11. 12-6. Application Example
R1 VIN ~ R2
C
R3
XTAL NETWORK
Figure 10. Frequency Response
20
GAIN (dB)
15 10 5 0
NARROW BAND BPF
VCC = 4.0V Vin = 50mV R1 = 18k R2 = 750 R3 = 390k C = 0.001F 1k 10k 100k fin , FILTER AMPLIFIER INPUT FREQUENCY (Hz)
VCC
PHASE SHIFTER
Eq. (3) is formularized, where G0 is the gain at center frequency f0, and 3dB bandwidth Q=f0/BW.
R3 R1R3 Q , R2 = , R3 = f 0C 2G0 4Q2R1-R3
R1 =
12-5. Squelch Section The output, which is controlled in accordance with the noise level from the rectifier, is injected into the squelch input pin. There is about 45mV of hysteresis at the Squelch Input to prevent jitter. Figure 11. Squelch Output versus Squelch Input i) Pin 13 Output
Scan Control(V)
ii) Pin 14 Output
Scan Control(V)
VTL
VTH
VSQ(V)
December 2000 TOKO, Inc.
+
VTL VTH VSQ(V)
C
VOUT
Figure 12: Application Example Block Digram
RF INPUT
1 OSC 2
MIXER
16
GND 15 MUTE
3 SQUELCH 4 VCC
14 SCAN CONTROL to PLL 13
RECTIFIER
5 0.1F 6
LIMIT AMP
12
0.1F 7
FILTER AMP
NETWORK
11
10 10pF
8 QUAD DET
9
LPF
(3)
AF OUTPUT
12-7. Attentions to Layout Design As this product is considered for stable operation, the mixer block and the other block that includes IF stage, OP amp and squelch are independent from each other. However in order to realize stable operation, please pay attention to the following, because of high frequency operation. (1) Bypass Capacitor A bypass capacitor must be connected with minimum distance between the VCC pin and the GND pin. (2) VCC/GND Pattern In order to make low impedance VCC/GND lines, please keep the pattern as wide as possible. (3) Pattern near Demodulator Pattern layout around the phase shifter for demodulator: please keep as short as possible.
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TK83361M
NOTES
WARNING - Life support applications policy. TOKO, Inc. products shall not be used within any life support systems without the specific written consent of TOKO, Inc. A life support system is a product or system intended to support or sustain life which, if it fails, can be reasonably expected to result in a significant personal injury or death. The contents of this application as of December 2000. The contents of this datasheet are subject to change without notice or stop manufacture. The circuits shown in this specification are intended to explain typical applications of the products concerned. Accordingly, TOKO, Inc. is not responsible for any circuit problems, or for any infringement of third party patents or any other intellectual property rights that may arise from the use of these circuits. Moreover, this specification dose not signify that TOKO, Inc. agrees implicitly or explicitly to license any patent rights or other intellectual property rights which it holds. No Ozone Depleting Substances (ODS) were used in the manufacture of these parts. Examples of characteristics given here are typical for each product and being technical data, these do not constitute a guarantee of characteristics or conditions of use.
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December 2000 TOKO, Inc.
TK83361M
PACKAGE OUTLINE
Marking Information Marking
0.76 TOKO Mark 16 Mark 9
SOP-16
TK83361M
83361
1.27
YYY
1 8 Lot No.
3.90.2
1.27 Recommended Mount Pad
9.90.2
0.2 0 ~ 0.25 1.45
1.75 max
0.50.2
0.4 -0.05
+0.15 0.1
1.27
0 ~ 10
0.12 M
Dimensions are shown in millimeters Tolerance: x.x = 0.2 mm (unless otherwise specified)
6.00.3
Toko America, Inc. Headquarters 1250 Feehanville Drive, Mount Prospect, Illinois 60056 Tel: (847) 297-0070 Fax: (847) 699-7864
TOKO AMERICA REGIONAL OFFICES
Midwest Regional Office Toko America, Inc. 1250 Feehanville Drive Mount Prospect, IL 60056 Tel: (847) 297-0070 Fax: (847) 699-7864 Western Regional Office Toko America, Inc. 2480 North First Street , Suite 260 San Jose, CA 95131 Tel: (408) 432-8281 Fax: (408) 943-9790 Semiconductor Technical Support Toko Design Center 4755 Forge Road Colorado Springs, CO 80907 Tel: (719) 528-2200 Fax: (719) 528-2375
Visit our Internet site at http://www.tokoam.com
The information furnished by TOKO, Inc. is believed to be accurate and reliable. However, TOKO reserves the right to make changes or improvements in the design, specification or manufacture of its products without further notice. TOKO does not assume any liability arising from the application or use of any product or circuit described herein, nor for any infringements of patents or other rights of third parties which may result from the use of its products. No license is granted by implication or otherwise under any patent or patent rights of TOKO, Inc.
December 2000 TOKO, Inc.
(c) 2000 Toko, Inc. All Rights Reserved IC-231-TK11031 0798O0.0K
0.2 -0.05
+0.15
5.4
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Printed in the USA

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