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| a FEATURES Low Cost Excellent Video Performance 55 MHz 0.1 dB Bandwidth (Gain = +2) 0.01% & 0.05 Differential Gain & Phase Errors High Speed 130 MHz Bandwidth (3 dB, G = +2) 100 MHz Bandwidth (3 dB, G+ = -1) 500 V/ s Slew Rate 80 ns Settling Time to 0.01% (VO = 10 V Step) High Output Drive Capability 50 mA Minimum Output Current Ideal for Driving Back Terminated Cables Flexible Power Supply Specified for Single (+5 V) and Dual ( 5 V to 15 V) Power Supplies Low Power: 7.5 mA max Supply Current Available in 8-Lead SOIC and 8-Lead Plastic Mini-DIP PRODUCT DESCRIPTION NULL -IN +IN -V S Low Cost, Low Power Video Op Amp AD818 CONNECTION DIAGRAMS 8-Lead Plastic Mini-DIP (N), and SOIC (R) Packages 1 2 3 4 AD818 8 7 6 5 NULL +VS OUTPUT NC TOP VIEW NC = NO CONNECT and 500 V/s slew rate make the AD818 useful in many high speed applications including: video monitors, CATV, color copiers, image scanners and fax machines. The AD818 is fully specified for operation with a single +5 V power supply and with dual supplies from 5 V to 15 V. This power supply flexibility, coupled with a very low supply current of 7.5 mA and excellent ac characteristics under all power supply conditions, make the AD818 the ideal choice for many demanding yet power sensitive applications. The AD818 is a voltage feedback op amp and excels as a gain stage in high speed and video systems (gain = >2 or -1). It achieves a settling time of 45 ns to 0.1%, with a low input offset voltage of 2 mV max. The AD818 is available in low cost, small 8-lead plastic miniDIP and SOIC packages. 0.02 The AD818 is a low cost, video op amp optimized for use in video applications which require gains equal to or greater than +2 or -1. The AD818 low differential gain and phase errors, single supply functionality, low power and high output drive make it ideal for cable driving applications such as video cameras and professional video equipment. With video specs like 0.1 dB flatness to 55 MHz and low differential gain and phase errors of 0.01% and 0.05, along with 50 mA of output current, the AD818 is an excellent choice for any video application. The 130 MHz 3 dB bandwidth (G = +2) +15V 0.01F 2.2F DIFF GAIN 0.01 VIN 7 3 Rbt 75 6 Rt 75 75 DIFFERENTIAL PHASE - Degrees AD818 2 4 0.06 0.00 0.05 DIFF PHASE 0.04 0.1F 2.2F -15V 1k 1k 0.03 5 10 SUPPLY VOLTAGE - Volts 15 AD818 Video Line Driver AD818 Differential Gain and Phase vs. Supply REV. B Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 World Wide Web Site: http://www.analog.com Fax: 781/326-8703 (c) Analog Devices, Inc., 2000 DIFFERENTIAL GAIN - Percent AD818-SPECIFICATIONS Parameter DYNAMIC PERFORMANCE -3 dB Bandwidth (@ TA = +25 C, unless otherwise noted) VS 5 V 15 V 0, +5 V 5 V 15 V 0, +5 V 5 V 15 V 0, +5 V 5 V 15 V 0, +5 V 5 V 15 V 5 V 15 V 0, +5 V 5 V 15 V 5 V 15 V 15 V 15 V 5 V 0, +5 V 15 V 5 V 0, +5 V 5 V to 15 V 350 450 250 Min 70 100 40 50 70 30 20 40 10 18 40 10 AD818A Typ Max 95 130 55 70 100 50 43 55 18 34 72 19 25.5 8.0 400 500 300 45 45 80 80 63 0.005 0.01 0.08 0.045 0.06 0.1 10 0.5 10 5 V, 15 V 3.3 Units MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz MHz V/s V/s V/s ns ns ns ns dB % % % Degrees Degrees Degrees pF mV mV V/C nA nA nA/C nA nA nA/C V/mV V/mV V/mV V/mV V/mV V/mV dB dB dB dB dB nV/Hz pA/Hz Conditions Gain = +2 Gain = -1 Bandwidth for 0.1 dB Flatness Gain = +2 CC = 2 pF Gain = -1 CC = 2 pF Full Power Bandwidth 1 Slew Rate Settling Time to 0.1% to 0.01% Total Harmonic Distortion Differential Gain Error (RL = 150 ) Differential Phase Error (RL = 150 ) Cap Load Drive INPUT OFFSET VOLTAGE VOUT = 5 V p-p RLOAD = 500 VOUT = 20 V p-p RLOAD = 1 k RLOAD = 1 k Gain = -1 -2.5 V to +2.5 V 0 V-10 V Step, A V = -1 -2.5 V to +2.5 V 0 V-10 V Step, A V = -1 FC = 1 MHz NTSC Gain = +2 NTSC Gain = +2 0.01 0.02 0.09 0.09 TMIN to TMAX Offset Drift INPUT BIAS CURRENT TMIN TMAX INPUT OFFSET CURRENT TMIN to TMAX Offset Current Drift OPEN-LOOP GAIN VOUT = 2.5 V RLOAD = 500 TMIN to TMAX RLOAD = 150 VOUT = 10 V RLOAD = 1 k TMIN to TMAX VOUT = 7.5 V RLOAD = 150 (50 mA Output) VCM = 2.5 V VCM = 12 V TMIN to TMAX VS = 5 V to 15 V TMIN to TMAX f = 10 kHz f = 10 kHz 5 V, 15 V 5 V, 15 V 5 V 3 2 2 6 3 3 5 V 15 V 15 V 82 86 84 80 80 5 4 9 0.3 5 V, 15 V 25 2 3 6.6 10 4.4 300 500 15 V 15 V 5 100 120 100 90 10 1.5 COMMON-MODE REJECTION POWER SUPPLY REJECTION INPUT VOLTAGE NOISE INPUT CURRENT NOISE -2- REV. B AD818 Parameter INPUT COMMON-MODE VOLTAGE RANGE Conditions VS 5 V 15 V 0, +5 V OUTPUT VOLTAGE SWING RLOAD = 500 RLOAD = 150 RLOAD = 1 k RLOAD = 500 RLOAD = 500 5 V 5 V 15 V 15 V 0, +5 V 15 V 5 V 0, +5 V 15 V Min +3.8 -2.7 +13 -12 +3.8 +1.2 3.3 3.2 13.3 12.8 +1.5, +3.5 50 50 30 AD818A Typ +4.3 -3.4 +14.3 -13.4 +4.3 +0.9 3.8 3.6 13.7 13.4 Max Units V V V V V V V V V V V mA mA mA mA k pF 18 +36 7.5 7.5 7.5 7.5 V V mA mA mA mA Output Current Short-Circuit Current INPUT RESISTANCE INPUT CAPACITANCE OUTPUT RESISTANCE POWER SUPPLY Operating Range Quiescent Current TMIN to TMAX TMIN to TMAX NOTE 1 Full power bandwidth = slew rate/2 VPEAK. Specifications subject to change without notice. 90 300 1.5 Open Loop Dual Supply Single Supply 2.5 +5 8 5 V 5 V 15 V 15 V 2.0 7.0 7.0 MAXIMUM POWER DISSIPATION - Watts TJ = 150C 8-LEAD MINI-DIP PACKAGE 1.5 ABSOLUTE MAXIMUM RATINGS 1 Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 V Internal Power Dissipation2 Plastic (N) . . . . . . . . . . . . . . . . . . . . . . See Derating Curves Small Outline (R) . . . . . . . . . . . . . . . . . See Derating Curves Input Voltage (Common Mode) . . . . . . . . . . . . . . . . . . . . VS Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . 6 V Output Short Circuit Duration . . . . . . . . See Derating Curves Storage Temperature Range (N, R) . . . . . . . -65C to +125C Operating Temperature Range . . . . . . . . . . . -40C to +85C Lead Temperature Range (Soldering 10 seconds) . . . . +300C NOTES 1 Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. 2 Specification is for device in free air: 8-lead plastic package, JA = 90C/W; 8-lead SOIC package, JA = 155C/W. 1.0 0.5 8-LEAD SOIC PACKAGE 0 -50 -40 -30 -20 -10 0 +10 +20 +30 +40 +50 +60 +70 +80 +90 AMBIENT TEMPERATURE - C Maximum Power Dissipation vs. Temperature for Different Package Types ESD SUSCEPTIBILITY ORDERING GUIDE Model AD818AN AD818AR Temperature Range -40C to +85C -40C to +85C Package Description 8-Lead Plastic DIP 8-Lead Plastic SOIC 13" Tape & Reel 7" Tape & Reel Package Option N-8 SO-8 SO-8 SO-8 ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 volts, which readily accumulate on the human body and on test equipment, can discharge without detection. Although the AD818 features proprietary ESD protection circuitry, permanent damage may still occur on these devices if they are subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid any performance degradation or loss of functionality. AD818AR-REEL -40C to +85C AD818AR-REEL7 -40C to +85C REV. B -3- AD818 -Typical Characteristics METALIZATION PHOTOGRAPH Dimensions shown in inches and (mm). 20 INPUT COMMON-MODE RANGE - Volts 600 15 +VCM 10 -VCM 5 SLEW RATE - V/s 500 400 300 0 0 5 10 SUPPLY VOLTAGE - Volts 15 20 200 0 5 15 10 SUPPLY VOLTAGE - Volts 20 Figure 1. Common-Mode Voltage Range vs. Supply 30 Figure 3. Slew Rate vs. Supply Voltage 20 OUTPUT VOLTAGE SWING - Volts p-p 25 VS = 15V 20 OUTPUT VOLTAGE SWING - Volts 15 RL = 500 10 15 10 VS = 5V 5 RL = 150 5 0 10 100 1k 10k LOAD RESISTANCE - 0 0 5 10 SUPPLY VOLTAGE - Volts 15 20 Figure 2. Output Voltage Swing vs. Load Resistance Figure 4. Output Voltage Swing vs. Supply -4- REV. B AD818 8.0 QUIESCENT SUPPLY CURRENT - mA 70 95 PHASE MARGIN PHASE MARGIN - Degrees +85C 7.0 -40C +25C 50 75 GAIN/BANDWIDTH 40 65 6.5 6.0 0 5 10 SUPPLY VOLTAGE - Volts 15 20 30 -60 -40 -20 0 20 40 60 80 TEMPERATURE - C 100 120 55 140 Figure 5. Quiescent Supply Current vs. Supply Voltage 100 Figure 8. -3 dB Bandwidth and Phase Margin vs. Temperature. Gain = +2 9 15V 8 OPEN-LOOP GAIN - V/mV CLOSED-LOOP OUTPUT IMPEDANCE - Ohms 10 7 5V 6 1 5 0.1 4 0.01 1k 10k 100k 1M 10M 100M FREQUENCY - Hz 3 100 1k LOAD RESISTANCE - Ohms 10k Figure 6. Closed-Loop Output Impedance vs. Frequency 7 Figure 9. Open-Loop Gain vs. Load Resistance 130 SHORT CIRCUIT CURRENT - mA 6 INPUT BIAS CURRENT - A 110 SOURCE CURRENT 90 SINK CURRENT 70 5 4 3 2 50 1 -60 -40 -20 0 20 40 60 80 100 120 140 30 -60 -40 -20 0 20 40 60 80 100 120 140 TEMPERATURE - C TEMPERATURE - C Figure 7. Input Bias Current vs. Temperature Figure 10. Short Circuit Current vs. Temperature REV. B -5- -3dB BANDWIDTH - MHz 7.5 60 85 AD818-Typical Characteristics 100 PHASE 5V OR 15V SUPPLIES +100 10 8 OUTPUT SWING FROM 0 TO V 80 OPEN-LOOP GAIN - dB +80 15V SUPPLIES RL = 1k PHASE MARGIN - Degrees 6 4 1% 2 0 -2 -4 -6 -8 1% 0.1% 0.01% 0.1% 0.01% 60 +60 40 5V SUPPLIES RL = 1k 20 +40 +20 0 0 -20 1k 10k 100k 1M 10M FREQUENCY - Hz 100M 1G -10 0 20 40 60 80 100 SETTLING TIME - ns 120 140 160 Figure 11. Open-Loop Gain and Phase Margin vs. Frequency 100 90 80 +SUPPLY 70 Figure 14. Output Swing and Error vs. Settling Time 50 INPUT VOLTAGE NOISE - nV/ Hz 40 PSR - dB 30 60 50 -SUPPLY 40 30 20 10 100 20 10 0 1k 10k 100k 1M 10M 100M 1 10 100 FREQUENCY - Hz 1k 10k FREQUENCY - Hz 100k 1M 10M Figure 12. Power Supply Rejection vs. Frequency 120 Figure 15. Input Voltage Noise Spectral Density vs. Frequency 30 100 OUTPUT VOLTAGE - Volts p-p RL = 1k 20 CMR - dB 80 R = 150 L 10 60 40 1k 10k 100k FREQUENCY - Hz 1M 10M 0 100k 1M 10M FREQUENCY - Hz 100M Figure 13. Common-Mode Rejection vs. Frequency Figure 16. Output Voltage vs. Frequency -6- REV. B AD818 -40 RL = 150 2V p-p CC 10 9 8 VS CC 0.1dB Flatness 1k VIN 1k AD818 150 -50 HARMONIC DISTORTION - dB -60 15V 2pF 55 MHz 5V 1pF 43 MHz +5V 1pF 18 MHz VOUT GAIN - dB 7 6 5 -70 2nd HARMONIC -80 3rd HARMONIC -90 5V 4 3 +5V 2 15V -100 100 1k 10k 100k 1M 10M 1 1M FREQUENCY - Hz 10M 100M FREQUENCY - Hz 1G Figure 17. Harmonic Distortion vs. Frequency 650 Figure 20. Closed-Loop Gain vs. Frequency (G = +2) 10 8 6 VS 0.1dB FLATNESS 15V 72 MHz 5V 34 MHz +5V 19 MHz 2pF 1k VIN 1k AD818 150 550 SLEW RATE - V/s VOUT 4 GAIN - dB 2 0 15V -2 -4 +5V 5V -8 450 350 -6 250 -60 -40 -20 0 20 40 60 80 TEMPERATURE - C 100 120 140 -10 1M 10M 100M FREQUENCY - Hz 1G Figure 18. Slew Rate vs. Temperature 0.02 Figure 21. Closed-Loop Gain vs. Frequency (G = -1) DIFFERENTIAL GAIN - Percent DIFF GAIN 0.01 DIFFERENTIAL PHASE - Degrees 0.06 0.00 0.05 DIFF PHASE 0.04 0.03 5 10 SUPPLY VOLTAGE - Volts 15 Figure 19. Differential Gain and Phase vs. Supply Voltage REV. B -7- AD818-Typical Characteristics CF 1k 5V +VS 3.3F 100 90 50ns 0.01F HP VIN PULSE (LS) OR FUNCTION (SS) GENERATOR 1k 2 50 7 AD818 3 4 6 VOUT 0.01F TEKTRONIX P6201 FET PROBE TEKTRONIX 7A24 PREAMP 10 0% RL 3.3F -VS 5V Figure 22. Inverting Amplifier Connection Figure 25. Inverter Large Signal Pulse Response 15 VS, CF = 1 pF, RL = 1 k 2V 100 90 50ns 100 90 200mV 10ns 10 0% 10 0% 2V 200mV Figure 23. Inverter Large Signal Pulse Response 5 VS, CF = 1 pF, RL = 1 k 200mV 100 90 Figure 26. Inverter Small Signal Pulse Response 15 VS, CF = 1 pF, RL = 150 200mV 100 90 10ns 10ns 10 0% 10 0% 200mV 200mV Figure 24. Inverter Small Signal Pulse Response 5 VS, CF = 1 pF, RL = 150 Figure 27. Inverter Small Signal Pulse Response 5 VS, CF = 0 pF, RL = 150 -8- REV. B AD818 CF 1k 1k 5V +VS 3.3F 100 90 50ns 0.01F 2 HP VIN PULSE (LS) OR FUNCTION (SS) GENERATOR 100 3 50 7 AD818 4 6 VOUT 0.01F TEKTRONIX P6201 FET PROBE TEKTRONIX 7A24 PREAMP 10 0% RL 3.3F -VS 5V Figure 28. Noninverting Amplifier Connection Figure 31. Noninverting Large Signal Pulse Response 15 V, CF = 1 pF, RL = 1 k 2V 100 90 50ns 100 90 100mV 10ns 10 0% 10 0% 2V 200mV Figure 29. Noninverting Large Signal Pulse Response 5 V, CF = 1 pF, RL = 1 k Figure 32. Noninverting Small Signal Pulse Response 15 V, CF = 1 pF, RL = 150 100mV 100 90 10ns 100 90 100mV 10ns 10 0% 10 0% 200mV 200mV Figure 30. Noninverting Small Signal Pulse Response 5 V, CF = 1 pF, RL = 150 Figure 33. Noninverting Small Signal Pulse Response 5 V, CF = 0 pF, RL = 150 REV. B -9- AD818 +V S may result in peaking. A small capacitance (1-5 pF) may be used in parallel with the feedback resistor to neutralize this effect. Power supply leads should be bypassed to ground as close as possible to the amplifier pins. Ceramic disc capacitors of 0.1 F are recommended. +VS 2 7 OUTPUT -IN +IN AD818 3 4 -VS NULL 1 NULL 8 6 8 1 10k VOS ADJUST -VS Figure 34. AD818 Simplified Schematic THEORY OF OPERATION Figure 35. Offset Null Configuration OFFSET NULLING The AD818 is a low cost, video operational amplifier designed to excel in high performance, high output current video applications. The AD818 (Figure 34) consists of a degenerated NPN differential pair driving matched PNPs in a folded-cascode gain stage. The output buffer stage employs emitter followers in a class AB amplifier which delivers the necessary current to the load, while maintaining low levels of distortion. The AD818 will drive terminated cables and capacitive loads of 10 pF or less. As the closed-loop gain is increased, the AD818 will drive heavier cap loads without oscillating. INPUT CONSIDERATIONS The input offset voltage of the AD818 is inherently very low. However, if additional nulling is required, the circuit shown in Figure 35 can be used. The null range of the AD818 in this configuration is 10 mV. SINGLE SUPPLY OPERATION Another exciting feature of the AD818 is its ability to perform well in a single supply configuration. The AD818 is ideally suited for applications that require low power dissipation and high output current. Referring to Figure 36, careful consideration should be given to the proper selection of component values. The choices for this particular circuit are: R1 + R3 R2 combine with C1 to form a low frequency corner of approximately 10 kHz. C4 was inserted in series with R4 to maintain amplifier stability at high frequency. Combining R3 with C2 forms a low pass filter with a corner frequency of approximately 500 Hz. This is needed to maintain amplifier PSRR, since the supply is connected to VIN through the input divider. The values for R2 and C2 were chosen to demonstrate the AD818's exceptional output drive capability. In this configuration, the output is centered around 2.5 V. In order to eliminate the static dc current associated with this level, C3 was inserted in series with RL. +VS R3 100 C2 3.3 F An input protection resistor (RIN in Figure 28) is required in circuits where the input to the AD818 will be subjected to transient of continuous overload voltages exceeding the 6 V maximum differential limit. This resistor provides protection for the input transistors by limiting their maximum base current. For high performance circuits, it is recommended that a "balancing" resistor be used to reduce the offset errors caused by bias current flowing through the input and feedback resistors. The balancing resistor equals the parallel combination of RIN and RF and thus provides a matched impedance at each input terminal. The offset voltage error will then be reduced by more than an order of magnitude. GROUNDING AND BYPASSING When designing high frequency circuits, some special precautions are in order. Circuits must be built with short interconnect leads. When wiring components, care should be taken to provide a low resistance, low inductance path to ground. Sockets should be avoided, since their increased interlead capacitance can degrade circuit bandwidth. Feedback resistors should be of low enough value (1 k) to assure that the time constant formed with the inherent stray capacitance at the amplifier's summing junction will not limit performance. This parasitic capacitance, along with the parallel resistance of RF/RIN, form a pole in the loop transmission which R4 1k C4 0.001 F 1k 3.3 F SELECT C1, R1, R2 FOR DESIRED LOW FREQUENCY CORNER. 0.01 F R1 3.3k C1 0.01 F VIN R2 3.3k 3 2 7 AD818 4 6 VOUT RL 150 C3 0.1 F Figure 36. Single Supply Amplifier Configuration -10- REV. B AD818 ERROR AMPLIFIER VERROR OUTPUT x 10 ERROR SIGNAL OUTPUT 2x HP2835 2 0.01F 0 TO 10V POWER SUPPLY EI&S DL1A05GM MERCURY RELAY 7, 8 2 TTL LEVEL SIGNAL GENERATOR 50Hz OUTPUT 13 1, 14 50 COAX CABLE 0.47F NULL ADJUST 1k FALSE SUMMING NODE 500 1k 100 NOTE: USE CIRCUIT BOARD WITH GROUND PLANE DEVICE UNDER TEST 10pF SCOPE PROBE CAPACITANCE 0.01F TEKTRONIX P6201 FET PROBE TO TEKTRONIX TYPE 11402 OSCILLOSCOPE PREAMP INPUT SECTION SETTLING OUTPUT 1.9k +VS 0.01F -VS 2x HP2835 3 5 100 6 4 7 0.47F 1M 15pF SHORT, DIRECT CONNECTION TO TEKTRONIX TYPE 11402 OSCILLOSCOPE PREAMP INPUT SECTION AD829 100 5-18pF 500 50 2 AD818 3 7 4 6 DIGITAL GROUND ANALOG GROUND 2.2F 2.2F 0.01F -VS +VS Figure 37. Settling Time Test Circuit AD818 SETTLING TIME DIFFERENTIAL LINE RECEIVER Settling time is comprised primarily of two regions. The first is the slew time in which the amplifier is overdriven, where the output voltage rate of change is at its maximum. The second is the linear time period required for the amplifier to settle to within a specified percent of the final value. Measuring the rapid settling time of AD818 (45 ns to 0.1% and 80 ns to 0.01%--10 V step) requires applying an input pulse with a very fast edge and an extremely flat top. With the AD818 configured in a gain of -1, a clamped false summing junction responds when the output error is within the sum of two diode voltages (approximately 1 volt). The signal is then amplified 20 times by a clamped amplifier whose output is connected directly to a sampling oscilloscope. A High Performance Video Line Driver The differential receiver circuit of Figure 39 is useful for many applications from audio to video. It allows extraction of a low level signal in the presence of common-mode noise. As shown in Figure 40, the AD818 provides this function with only 10 nV/Hz noise at the output. 2pF 1k +5V 0.01 F 2 DIFFERENTIAL INPUT 3 7 2.2 F 1k AD818 4 6 VOUT 2.2 F OUTPUT 0.01 F -5V 1k 2pF 1k The buffer circuit shown in Figure 38 will drive a back-terminated 75 video line to standard video levels (1 V p-p) with 0.1 dB gain flatness to 55 MHz with only 0.05 and 0.01% differential phase and gain at the 3.58 MHz NTSC subcarrier frequency. This level of performance, which meets the requirements for high-definition video displays and test equipment, is achieved using only 7 mA quiescent current. +15V 0.01F VIN Rt 75 3 2 7 2.2F Rbt 75 6 Rt 75 0.01F 1k 1k -15V 10 0% 100 90 Figure 39. Differential Line Receiver 200 V 1V 10n s 20ns 75 AD818 4 2.2F 2V Figure 38. Video Line Driver 200m V Figure 40. Performance of Line Receiver, RL = 150 , G = +2 REV. B -11- AD818 A HIGH SPEED, THREE OP AMP IN AMP OUTLINE DIMENSIONS Dimensions shown in inches and (mm). The circuit of Figure 41 uses three high speed op amps: two AD818s and an AD817. This high speed circuit lends itself well to CCD imaging and other video speed applications. It has the optional flexibility of both dc and ac trims for common-mode rejection, plus the ability to adjust for minimum settling time. EACH AMPLIFIER PIN 7 EACH AMPLIFIER 1F 0.1F 8-Lead Plastic Mini-DIP (N) Package 8 PIN 1 1 4 0.30 (7.62) REF 0.0350.01 (0.890.25) 5 +15V 10F COMMON 10F -15V +VS 0.1F 0.39 (9.91) MAX 0.1F -VS 1F 0.1F PIN 4 EACH AMPLIFIER 0.1650.01 (4.190.25) 0.125 (3.18) MIN 0.0180.003 (0.460.08) 0.10 (2.54) BSC 0.033 (0.84) NOM 0.180.03 (4.570.76) 0.0110.003 (0.280.08) 15 0 -VIN A1 AD818 1k 2-8 pF SETTLING TIME A.C. CMR ADJUST SEATING PLANE 1k 1k 5pF 2pF RG 5pF 1k 3pF 1k 970 PIN 1 8-Lead SOIC (R) Package VOUT 0.1968 (5.00) 0.1890 (4.80) RL 2k 8 5 4 A3 AD817 0.1574 (4.00) 0.1497 (3.80) 1 0.2440 (6.20) 0.2284 (5.80) A2 AD818 +VIN 50 D.C. CMR ADJUST 0.0500 (1.27) BSC 0.0098 (0.25) 0.0040 (0.10) SEATING PLANE 0.0688 (1.75) 0.0532 (1.35) 0.0192 (0.49) 0.0138 (0.35) 8 0.0098 (0.25) 0 0.0075 (0.19) 0.0196 (0.50) 0.0099 (0.25) 45 BANDWIDTH, SETTLING TIME, & TOTAL HARMONIC DISTORTION VS. GAIN SMALL SIGNAL BANDWIDTH 14.7 MHz 4.5 MHz 960 kHz SETTLING TIME TO 0.1% 200ns 370ns 2.5s THD + NOISE BELOW INPUT LEVEL @ 10kHz 82 dB 81 dB 71 dB 0.0500 (1.27) 0.0160 (0.41) GAIN 3 10 100 RG 1k 222 20 CADJ (pF) 2-8 2-8 2-8 Figure 41. High Speed 3 Op Amp In Amp -12- REV. B PRINTED IN U.S.A. C1738-0-5/00 (rev. B) 00872 0.25 (6.35) 0.31 (7.87) |
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