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clc410 fast settling, video op amp with disable general description the current-feedback clc410 is a fast settling, wideband, monolithic op amp with fast disable/enable feature. de- signed for low gain applications (a v = 1to 8), the clc410 consumes only 160mw of power (180mw max) yet provides a -3db bandwidth of 200mhz (a v = +2) and 0.05% settling in 12ns (15ns max). plus, the disable feature pro- vides fast turn on (100ns) and turn off (200ns). in addition, the clc410 offers both high performance and stability with- out compensation - even at a gain of +1. the clc410 provides a simple, high performance solution for video switching and distribution applications, especially where analog buses benefit from use of the disable function to amultiplexo signals onto the bus. differential gain/phase of 0.01%/0.01 provide high fidelity and the 60ma output cur- rent offers ample drive capability. the clc410's fast settling, low distortion, and high drive capabilities make it an ideal adc driver. the low 160mw quiescent power consumption and very low 40mw disabled power consumption suggest use where power is critical and/or asystem offo power consumption must be minimized. the clc410 is available in several versions to meet a variety of requirements. a three letter suffix determines the version. enhanced solutions (military/aerospace) smd number: 5962-90600 space level versions also available. for more information, visit http://www.national.com/mil features n -3db bandwidth of 200mhz n 0.05% settling in 12ns n low power, 160mw (40mw disabled) n low distortion, -60dbc at 20mhz n fast disable (200ns) n differential gain/phase: 0.01%/0.01 n 1to 8 closed-loop gain range applications n video switching and distribution n analog bus driving (with disable) n low power astandbyo using disable n fast, precision a/d conversion n d/a current-to-voltage conversion n if processors n high speed communications connection diagram enable/disable response ds012749-10 ds012749-21 pinout dip & soic february 2001 clc410 fast settling, video op amp with disable ? 2001 national semiconductor corporation ds012749 www.national.com
connection diagram (continued) ordering information package temperature range industrial part number package marking nsc drawing 8-pin plastic dip ?40c to +85c CLC410AJP CLC410AJP n08a 8-pin plastic soic ?40c to +85c clc410aje clc410aje m08a ds012749-1 non-inverting frequency response clc410 www.national.com 2
absolute maximum ratings (note 1) if military/aerospace specified devices are required, please contact the national semiconductor sales office/ distributors for availability and specifications. supply voltage (v cc ) 7v i out output is short circuit protected to ground, but maximum reliability will be maintained if i out does not exceed... 60ma common mode input voltage v cc differential input voltage 5v disable input voltage (pin 8) v cc ?1v applied output voltage when disabled v cc junction temperature +150c operating temperature range ?40c to +85c storage temperature range ?65c to +150c lead solder duration (+300c) 10 sec esd rating (human body model) 500v operating ratings thermal resistance package ( q jc )( q ja ) mdip 65c/w 120c/w soic 60c/w 140c/w electrical characteristics a v = +2, v cc = 5v, r l = 100 w ,r f = 250 w ; unless specified symbol parameter conditions typ max/min (note 2) units ambient temperature clc410aj +25c ?40c +25c +85c frequency domain response ssbw -3db bandwidth v out < 0.5v pp 200 > 150 > 150 > 120 mhz lsbw v out < 5v pp ,a v = +5 50 > 35 > 35 > 35 mhz gain flatness v out < 0.5v pp gfpl peaking dc to 40mhz 0 < 0.4 < 0.3 < 0.4 db gfph peaking > 40mhz 0 < 0.7 < 0.5 < 0.7 db gfr rolloff dc to 75mhz 0.6 < 1 < 1 < 1.3 db lpd linear phase deviation dc to 75mhz 0.2 < 1 < 1 < 1.2 deg time domain response trs rise and fall time 0.5v step 1.6 < 2.4 < 2.4 < 2.4 ns trl 5v step 6.5 < 10 < 10 < 10 ns tsp settling time to 0.1% 2v step 10 < 13 < 13 < 13 ns ts 0.05% 2v step 12 < 15 < 15 < 15 ns os overshoot 0.5v step 0 < 15 < 10 < 10 % sr slew rate a v = +2 700 > 430 > 430 > 430 v/s sr1 a v = ?2 1600 v/s distortion and noise response hd2 2nd harmonic distortion 2v pp , 20mhz ?60 < ?40 < ?45 < ?45 dbc hd3 3rd harmonic distortion 2v pp , 20mhz ?60 < ?50 < ?50 < ?50 dbc equivalent input noise snf noise floor > 1mhz (note 4) ?157 < ?154 < ?154 < ?153 dbm (1hz) inv integrated noise 1mhz to 200mhz (note 4) 40 < 54 < 57 < 63 v dg differential gain (note 5) (see plots) 0.01 0.05 0.04 0.04 % dp differential phase (note 5) (see plots) 0.01 0.1 0.02 0.02 deg disable/enable performance toff disable time to > 50db attenuation at 10mhz 200 < 1000 < 1000 < 1000 ns ton enable time 100 < 200 < 200 < 200 ns dis voltage vdis to disable 1.0 0.5 0.5 0.5 v ven to enable 2.6 2.3 3.2 4.0 v clc410 www.national.com 3
electrical characteristics (continued) a v = +2, v cc = 5v, r l = 100 w ,r f = 250 w ; unless specified symbol parameter conditions typ max/min (note 2) units disable/enable performance dis current (sourced from clc410, see figure 5 ) idis to disable 200 250 250 250 a ien to enable 80 60 60 60 a osd off isolation at 10mhz 59 > 55 > 55 > 55 db static, dc performance vio input offset voltage (note 3) 2 < 8.2 < 5.0 < 9.0 mv dvio average temperature coefficient 20 < 40 < 40 v/c ibn input bias current (note 3) non inverting 10 < 36 < 20 < 20 a dibn average temperature coefficient 100 < 200 < 100 na/c ibi input bias current (note 3) inverting 10 < 36 < 20 < 30 a dibi average temperature coefficient 50 < 200 < 100 na/c psrr power supply rejection ratio 50 > 45 > 45 > 45 db cmrr common mode rejection ratio 50 > 45 > 45 > 45 db icc supply current (note 3) no load,quiescent 16 < 18 < 18 < 18 ma isd supply current, disabled no load,quiescent 4 < 6 < 6 < 6ma miscellaneous performance rin non-inverting input resistance 200 > 50 > 100 > 100 k w cin capacitance 0.5 < 2 < 2 < 2pf ro output impedance at dc 0.1 < 0.2 < 0.2 < 0.2 w rod output impedance, disabled resistance,at dc 200 < 100 < 100 < 100 k w cod capacitance,at dc 0.5 < 2 < 2 < 2pf vo output voltage range no load 3.5 > 3 > 3.2 > 3.2 v cmir common mode input range for rated performance 2.1 > 1.2 > 2 > 2v io output current ?40c to +85c 70 > 30 > 50 > 50 ma io ?55c to +125c 60 > 30 > 50 > 50 ma note 1: aabsolute maximum ratingso are those values beyond which the safety of the device cannot be guaranteed. they are not meant to imply that the devices should be operated at these limits. the table of aelectrical characteristicso specifies conditions of device operation. note 2: min/max ratings are based on product characterization and simulation. individual parameters are tested as noted. outgoing quality levels are deter mined from tested parameters. note 3: aj-level: spec. is 100% tested at +25c, sample at 85c. note 4: noise tests are performed from 5mhz to 200mhz. note 5: differential gain and phase measured at: a v = +2, r f = 250 w ,r l = 150 w 1v pp equivalent video signal, 0-100 ire, 40 ire pp , 3.58 mhz,) ire =0 volts, at 75 w load. see text. clc410 www.national.com 4
typical performance characteristics (t a = 25, a v = +2, v cc = 5v, r l = 100 w ; unless specified). non-inverting frequency response ds012749-1 inverting frequency response ds012749-2 frequency response for various r l s ds012749-3 forward and reverse gain during disable ds012749-4 2nd and 3rd harmonic distortion ds012749-5 2-tone, 3rd order, intermodulation intercept ds012749-6 clc410 www.national.com 5
typical performance characteristics (t a = 25, a v = +2, v cc = 5v, r l = 100 w ; unless specified).. (continued) equivalent input noise ds012749-7 cmrr and psrr ds012749-8 pulse response ds012749-28 settling time ds012749-23 long-term settling time ds012749-24 settling time vs. capacitive load ds012749-9 clc410 www.national.com 6
typical performance characteristics (t a = 25, a v = +2, v cc = 5v, r l = 100 w ; unless specified).. (continued) application division enable/disable response ds012749-10 differential gain and phase (3.58mhz) ds012749-11 differential gain and phase (4.43mhz) ds012749-12 ds012749-13 figure 1. recommended non-inverting gain circuit clc410 www.national.com 7
application division (continued) enable/disable operation the clc410 has an enable/disable feature that is useful for conserving power and for multiplexing the outputs of several amplifiers onto an analog bus ( figure 3 ). disabling an am- plifier while not in use reduces power supply current and the output and inverting input pins become a high impedance. pin 8, the dis pin, can be driven from either open-collector ttl or from 5v cmos. a logic low disables the amplifier and an internal 15k w pull-up resistor ensures that the amplifier is enabled if pin 8 is not connected ( figure 5 ). both ttl and 5v cmos logic are guaranteed to drive a high enough high-level output voltage (v oh ) to ensure that the clc410 is enabled. whichever type used, abreak-before-makeo opera- tion should be established when outputs of several amplifi- ers are connected together. this is important for avoiding large, transient currents flowing between amplifiers when two or more are simultaneously enabled. typically, proper operation is ensured if all the amplifiers are driven from the same decoder integrated circuit because logic output rise times tend to be longer than fall times. as a result, the ds012749-14 figure 2. recommended inverting gain circuit ds012749-15 figure 3. ds012749-16 figure 4. clc410 www.national.com 8
application division (continued) amplifier being disabled will reach the 2v threshold sooner than the amplifier being enabled (see t d of figure 4 timing diagram). during disable, supply current drops to approximately 4ma and the inverting input and output pin impedances become 200k w \ 0.5pf each. the total impedance that a disabled amplifier and its associated feedback network presents to the analog bus is determined from figure 6 . for example, at a non-inverting gain of 1, the output impedance at video frequencies is 100k w \ 1pf since the 250 w feedback resistor is a negligible impedance. similarly, output impedance is 500 w \ 0.5pf at a non-inverting gain of 2 (with r f =r g = 250 w ). differential gain and phase plots on the preceding page illustrate the differential gain and phase performance of the clc410 at both 3.58mhz and 4.43mhz. application note oa-08 presents a measurement technique for measuring the very low differential gain and phase of the clc410. observe that the gain and phase errors remain low even as the output loading increases, making the device attractive for driving multiple video out- puts. understanding the loop gain the clc410 is a current-feedback op amp. referring to the equivalent circuit of figure 7 , any current flowing in the inverting input is amplified to a voltage at the output through the transimpedance gain shown below. this z(s) is analo- gous to the open-loop gain of a voltage feedback amplifier. developing the non-inverting frequency response for the topology of figure 3 yields: (1) where lg is the loop gain defined by, (2) equation 1 has a form identical to that for a voltage feedback amplifier with the differences occurring in the lg expression, eq.2. for an idealized treatment, set z i = 0 which results in a very simple lg=z(s)/r f (derivation of the transfer function for the case where z i = 0 is given in application note an300-1). using the z(s) (open-loop transimpedance gain) plot shown on the previous page and dividing by the recom- mended r f = 250 w , yields a large loop gain at dc. as a result, equation 1 shows that the closed-loop gain at dc is very close to (1+r f /r g ). at higher frequencies, the roll-off of z(s) determines the closed-loop frequency response which, ideally, is dependent only on r f . the specifications reported on the previous pages are therefore valid only for the specified r f = 250 w . increasing r f from 250 w will decrease the loop gain and band width, while decreasing it will increase the loop gain possibly leading to inadequate phase margin and ds012749-17 figure 5. equivalent of (not) dis input ds012749-18 figure 6. ds012749-19 open-loop transimpedance gain, z(s) ds012749-20 figure 7. current feedback topology clc410 www.national.com 9
application division (continued) closed-loop peaking. conversely, fixing r f will hold the fre- quency response constant while the closed-loop gain can be adjusted using r g . the clc410 departs from this idealized analysis to the extent that the inverting input impedance is finite. with the low quiescent power of the clc410, z i ) 50 w leading to drop in loop gain and bandwidth at high gain settlings, as given by equation 2. the second term in equation 2 accounts for the division in feedback current that occurs between z i and r f i r g at the inverting node of the clc410. this decrease in bandwidth can be circumvented as described in aincreasing bandwidth at high gains.o also see acurrent feedback am- plifierso in the national databook for a thorough discussion of current feedback op amps. increasing bandwidth at high gains bandwidth may be increased at high closed-loop gains by adjusting r f and r g to make up for the losses in loop gain that occur at these high gain settlings due to current division at the inverting input. an approximate relationship may be obtained by holding the lg expression constant as the gain is changed from the design point used in the specifications (that is, r f = 250 w and r g = 250 w ). for the clc400 this gives, (3) where a v is the non-inverting gain. note that with a v =+2we get the specified r f = 250 w , while at higher gains, a lower value gives stable performance with improved bandwidth. dc accuracy and noise since the two inputs for the clc410 are quite dissimilar, the noise and offset error performance differs somewhat from that of a standard differential input amplifier. specifically, the inverting input current noise is much larger than the non-inverting current noise. also the two input bias currents are physically unrelated rendering bias current cancellation through matching of the inverting and non-inverting pin re- sistors ineffective. in equation 4, the output offset is the algebraic sum of the equivalent input voltage and current sources that influence dc operation. output noise is determined similarly except that a root-sum-of-squares replaces the algebraic sum. r s is the non-inverting pin resistance. equation 4 output offset v o = ibnx r s (1+r f /r g ) vio (1+r f /r g ) ibix r f an important observation is that for fixed r f , offsets as referred to the input improve as the gain is increased (divide all terms by 1+r f /r g ). a similar result is obtained for noise where noise figure improves as a gain increases. the input noise plot shown in the clc400 datasheet applies equally as well to the clc410. capacitive feedback capacitive feedback should not be used with the clc410 because of the potential for loop instability. see application note oa-7 for active filter realizations with the clc410. offset adjustment pin pin 1 can be connected to a potentiometer as shown in figure 1 and used to adjust the input offset of the clc410. full range adjustment of 5v on pin 1 will yield a 10mv input offset adjustment range. pin 1 should always be by- passed to ground with a ceramic capacitor located close to the package for best settling performance. printed circuit layout as with any high frequency device, a good pcb layout will enhance performance. ground plane construction and good power supply bypassing close to the package are critical to achieving full performance. in the non-inverting configura- tion, the amplifier is sensitive to stray capacitance to ground at the inverting input. hence, the inverting node connections should be small with minimal coupling to the ground plane. shunt capacitance across the feedback resistor should not be used to compensate for this effect. parasitic or load capacitance directly on the output will intro- duce additional phase shift in the loop degrading the loop phase margin and leading to frequency response peaking. a small series resistor before the capacitance effectively de- couples this effect. the graphs on the preceding page illus- trates the required resistor value and resulting performance vs. capacitance. precision buffed resistors (prp8351 series from precision resistive products) with low parasitic reactances were used to develop the data sheet specifications. precision carbon composition resistors will also yield excellent results. stan- dard spirally-trimmed rn55d metal film resistors will work with a slight decrease in bandwidth due to their reactive nature at high frequencies. evaluation pc boards (part no. 730013 for through-hole and 730027 for soic) for the clc404 are available. clc410 www.national.com 10
physical dimensions inches (millimeters) unless otherwise noted 8-pin soic ns package number m08a clc410 www.national.com 11
physical dimensions inches (millimeters) unless otherwise noted (continued) life support policy national's products are not authorized for use as critical components in life support devices or systems without the express written approval of the president and general counsel of national semiconductor corporation. as used herein: 1. life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. a critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. national semiconductor corporation americas tel: 1-800-272-9959 fax: 1-800-737-7018 email: support@nsc.com national semiconductor europe fax: +49 (0) 180-530 85 86 email: europe.support@nsc.com deutsch tel: +49 (0) 69 9508 6208 english tel: +44 (0) 870 24 0 2171 fran?ais tel: +33 (0) 1 41 91 8790 national semiconductor asia pacific customer response group tel: 65-2544466 fax: 65-2504466 email: ap.support@nsc.com national semiconductor japan ltd. tel: 81-3-5639-7560 fax: 81-3-5639-7507 www.national.com 8-pin mdip ns package number n08e clc410 fast settling, video op amp with disable national does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and national reserves the righ t at any time without notice to change said circuitry and specifications.

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