1 ? fn9282.0 isl6594d advanced synchronous rectified buck mosfet drivers with protection features the isl6594d is high frequency mosfet driver specifically designed to drive upper and lower power n-channel mosfets in a synchronous rectified buck converter topology. this driver combined with the isl6594d digital multi-phase buck pwm controller and n-channel mosfets forms a complete core-voltage regulator solution for advanced microprocessors. the isl6594d drives both upper and lower gates over a range of 4.5v to 13.2v. this drive-voltage provides the flexibility necessary to optimize applications involving trade- offs between gate charge and conduction losses. an advanced adaptive zero shoot-through pr otection is integrated to prevent both the upper and lower mosfets from conducting simultaneously and to minimize the dead time. the isl6594d includes an overvoltage protection feature operational before vcc exceeds its turn-on threshold, at which the ph ase node is connected to the gate of the low side mosfet (lgate). the output voltage of the converter is then limited by the threshold of the low side mosfet, which provides some protection to the microprocessor if the upper mosfet(s) is shorted. the isl6594d also features an in put that recognizes a high- impedance state, working toget her with intersil multi-phase pwm controllers to prevent negative transients on the controlled output voltage when op eration is suspended. this feature eliminates the need for the schottky diode that may be utilized in a power system to protect the load from negative output voltage damage. features ? dual mosfet drives for sy nchronous rectified bridge ? pin-to-pin compatible with isl6596 ? advanced adaptive zero shoot-through protection - body diode detection - auto-zero of r ds(on) conduction offset effect ? adjustable gate voltage for optimal efficiency ? 36v internal bootstrap schottky diode ? bootstrap capacitor overcharging prevention ? supports high switching frequency (up to 2mhz) - 3a sinking current capability - fast rise/fall times and low propagation delays ? optimized for 3.3v pwm input ? three-state pwm input for output stage shutdown ? three-state pwm input hysteres is for applications with power sequencing requirement ? pre-por overvoltage protection ? vcc undervoltage protection ? expandable bottom copper pad for enhanced heat sinking ? dual flat no-lead (dfn) package - near chip-scale package footprint; improves pcb efficiency and thinner in profile ? pb-free plus anneal available (rohs compliant) applications ? optimized for pol dc/dc converters for iba systems ? core regulators for intel? and amd? microprocessors ? high current dc/dc converters ? high frequency and high efficiency vrm and vrd related literature technical brief tb363 ?guidelines for handling and processing moisture sensit ive surface mount devices (smds)? technical brief tb389 ?pcb land pattern design and surface mount guidelines for qfn (mlfp) packages? ordering information part number (note) part marking temp. range (c) package (pb-free) pkg. dwg. # isl6594dcbz 6594dcbz 0 to 85 8 ld soic m8.15 ISL6594DCBZ-T 6594dcbz 8 ld soic tape and reel isl6594dcrz 94dz 0 to 85 10 ld 3x3 dfn l10.3x3 isl6594dcrz-t 94dz 10 ld 3x3 dfn tape and reel note: intersil pb-free plus anneal products employ special pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish , which are rohs compliant and compatible with both snpb and pb-free soldering operations. intersil pb-free products are msl classi fied at pb-free peak reflow temperatures that meet or exceed the pb-free requirements of ipc/jedec j std-020. data sheet march 30, 2006 caution: these devices are sensitive to electrosta tic discharge; follow proper ic handling procedures. 1-888-intersil or 1-888-468-3774 | intersil (and design) is a registered trademark of intersil americas inc. copyright intersil americas inc. 2006. all rights reserved all other trademarks mentioned are the property of their respective owners.
2 fn9282.0 march 30, 2006 pinouts isl6594dcb (8ld soic) top view isl659dcr (10ld 3x3 dfn) top view ugate boot pwm gnd 1 2 3 4 8 7 6 5 phase pvcc vcc lgate 1 ugate boot n/c pwm phase pvcc n/c vcc 2 3 4 5 gnd 10 9 8 7 6 lgate gnd block diagram isl6594d pvcc vcc pwm +5v 13.6k 6.4k boot ugate phase lgate gnd for dfn devices, the pad on the bottom side of pad the package must be soldered to the circuit?s ground. uvcc = pvcc for isl6594d control logic por/ shoot- through protection pre-por ovp (lvcc) uvcc features isl6594d
3 fn9282.0 march 30, 2006 typical application - 4 channel converte r using isl6592 and isl6594d gate drivers +12v +5v rtherm +3.3v from p i2c i/f bus to p fault outputs isl6594d isl6594d isl6594d isl6594d vout rtn 8 7 5 6 8 7 5 6 8 7 5 6 8 7 5 6 1 2 4 3 1 2 4 3 1 2 4 3 1 2 4 3 isl6592 v12_sen gnd out1 out2 isen1 out3 out4 isen2 out5 out6 isen3 out7 out8 isen4 out9 out10 isen5 out11 out12 isen6 temp_sen cal_cur_en cal_cur_sen vsenp vsenn vdd vid4 vid3 vid2 vid1 vid0 vid5 ll0 ll1 outen vcc_pwrgd reset_n fault1 fault2 sda scl saddr isen5 ugate boot pwm gnd phase pvcc vcc lgate ugate boot pwm gnd phase pvcc vcc lgate ugate boot pwm gnd phase pvcc vcc lgate ugate boot pwm gnd phase pvcc vcc lgate isl6594d
4 fn9282.0 march 30, 2006 absolute maximum rati ngs thermal information supply voltage (vcc) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .15v supply voltage (pvcc) . . . . . . . . . . . . . . . . . . . . . . . . . vcc + 0.3v boot voltage (v boot-gnd ). . . . . . . . . . . . . . . . . . . . . . . . . . . .36v input voltage (v pwm ) . . . . . . . . . . . . . . . . . . . . . . gnd - 0.3v to 7v ugate. . . . . . . . . . . . . . . . . . . v phase - 0.3v dc to v boot + 0.3v v phase - 3.5v (<100ns pulse width, 2j) to v boot + 0.3v lgate . . . . . . . . . . . . . . . . . . . . . . gnd - 0.3v dc to v pvcc + 0.3v gnd - 5v (<100ns pulse width, 2j) to v pvcc + 0.3v phase. . . . . . . . . . . . . . . . . . . . . . . . . . . . gnd - 0.3v dc to 15v dc gnd - 8v (<400ns, 20j) to 30v (<200ns, v boot-gnd <36v)) esd rating human body model . . . . . . . . . . . . . . . . . . . . class i jedec std recommended operating conditions ambient temperature range . . . . . . . . . . . . . . . . . . . . . 0c to 85c maximum operating junction temperature . . . . . . . . . . . . . . 125c supply voltage, vcc . . . . . . . . . . . . . . . . . . . . . . . . . . 6.8v to 13.2v supply voltage range, pvcc . . . . . . . . . . . . . . . . 5v to 12v 10% thermal resistance ja (c/w) jc (c/w) soic package (note 1) . . . . . . . . . . . . 100 n/a dfn package (notes 2, 3) . . . . . . . . . . 48 7 maximum junction temperature (plastic package) . . . . . . . . 150c maximum storage temperature range . . . . . . . . . . . -65c to 150c maximum lead temperature (soldering 10s) . . . . . . . . . . . . . 300c (soic - lead tips only) caution: stresses above those listed in ?absolute maximum ratings? may cause permanent damage to the device. this is a stress o nly rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. notes: 1. ja is measured with the component mounted on a high effe ctive thermal conductivity test board in free air. 2. ja is measured in free air with the component mounted on a high ef fective thermal conductivity te st board with ?direct attach? fe atures. see tech brief tb379. 3. for jc , the ?case temp? location is the center of the exposed metal pad on the package underside. electrical specifications recommended operating conditions, unless otherwise noted. parameter symbol test conditions min typ max units vcc supply current bias supply current i vcc isl6594d, f pwm = 300khz, v vcc = 12v - 4.5 - ma i vcc isl6594d, f pwm = 1mhz, v vcc = 12v - 5 - ma gate drive bias current i pvcc isl6594d, f pwm = 300khz, v pvcc = 12v - 7.5 - ma i pvcc isl6594d, f pwm = 1mhz, v pvcc = 12v - 8.5 - ma power-on reset and enable vcc rising threshold 6.1 6.4 6.7 v vcc falling threshold 4.7 5.0 5.3 v pwm input (see timing diagram on page 6) input current i pwm v pwm = 3.3v - 400 - a v pwm = 0v - -350 - a pwm rising threshold (note 4) vcc = 12v - 1.70 - v pwm falling threshold (note 4) vcc = 12v - 1.30 - v typical three-state shutdown window vcc = 12v 1.23 - 1.82 v three-state lower gate falling threshold vcc = 12v - 1.18 - v three-state lower gate rising threshold vcc = 12v - 0.76 - v three-state upper gate rising threshold vcc = 12v - 2.36 - v three-state upper gate falling threshold vcc = 12v - 1.96 - v shutdown holdoff time t tsshd - 245 - ns ugate rise time (note 4) t ru v pvcc = 12v, 3nf load, 10% to 90% - 26 - ns lgate rise time (note 4) t rl v pvcc = 12v, 3nf load, 10% to 90% - 18 - ns isl6594d
5 fn9282.0 march 30, 2006 ugate fall time (note 4) t fu v pvcc = 12v, 3nf load, 90% to 10% - 18 - ns lgate fall time (note 4) t fl v pvcc = 12v, 3nf load, 90% to 10% - 12 - ns ugate turn-on propagation delay (note 4) t pdhu v pvcc = 12v, 3nf load, adaptive - 10 - ns lgate turn-on propagation delay (note 4) t pdhl v pvcc = 12v, 3nf load, adaptive - 10 - ns ugate turn-off propagation delay (note 4) t pdlu v pvcc = 12v, 3nf load - 10 - ns lgate turn-off propagation delay (note 4) t pdll v pvcc = 12v, 3nf load - 10 - ns lg/ug three-state propagation delay (note 4) t pdts v pvcc = 12v, 3nf load - 10 - ns output (note 4) upper drive source current i u_source v pvcc = 12v, 3nf load - 1.25 - a upper drive source impedance r u_source 150ma source current 1.4 2.0 3.0 upper drive sink current i u_sink v pvcc = 12v, 3nf load - 2 - a upper drive sink impedance r u_sink 150ma sink current 0.9 1.65 3.0 lower drive source current i l_source v pvcc = 12v, 3nf load - 2 - a lower drive source impedance r l_source 150ma source current 0.85 1.3 2.2 lower drive sink current i l_sink v pvcc = 12v, 3nf load - 3 - a lower drive sink impedance r l_sink 150ma sink current 0.60 0.94 1.35 note: 4. guaranteed by characterization. not 100% tested in production. electrical specifications recommended operating conditions, unless otherwise noted. (continued) parameter symbol test conditions min typ max units functional pin description package pin # pin symbol function soic dfn 1 1 ugate upper gate drive output. connect to gate of high-side power n-channel mosfet. 2 2 boot floating bootstrap supply pin for the upper gate driv e. connect the bootstrap capacitor between this pin and the phase pin. the bootstrap capacitor provides the charge to turn on the upper mosfet. see the internal bootstrap device section under description for gui dance in choosing the capacitor value. - 3, 8 n/c no connection. 3 4 pwm the pwm signal is the control input for the driver. the pwm signal can enter three distinct states during operation, see the three-state pwm input section under description for further details. connect this pin to the pwm output of the controller. 4 5 gnd bias and reference ground. all signals are referenced to this node. it is also the power ground return of the driver. 5 6 lgate lower gate drive output. connect to gate of the low-side power n-channel mosfet. 6 7 vcc its operating range is +6.8v to 13.2v. place a high qua lity low esr ceramic capacitor from this pin to gnd. 7 9 pvcc this pin supplies power to both upper and lower gate dr ives. its operating range is +4.5v to 13.2v. place a high quality low esr ceramic capacitor from this pin to gnd. 8 10 phase connect this pin to the source of the upper mosfet and the drain of the lower mosfet. this pin provides a return path for the upper gate drive. 9 11 pad connect this pad to the power ground plane (gnd) via thermally enhanced connection. isl6594d
6 fn9282.0 march 30, 2006 description operation designed for versatility and speed, the isl6594d mosfet driver control both high-side and low-side n-channel fets of a half-bridge power train from one externally provided pwm signal. prior to vcc exceeding its por level, the pre-por overvoltage protection function is activated during initial startup; the upper gate (ugate) is held low and the lower gate (lgate), controlled by the pre-por overvoltage protection circuits, is connec ted to the phase. once the vcc voltage surpasses the vcc rising threshold (see electrical specifications), t he pwm signal takes control of gate transitions. a rising edge on pwm initiates the turn-off of the lower mosfet (see timing diagram). after a short propagation delay [t pdll ], the lower gate begins to fall. typical fall times [t fl ] are provided in the electrical specifications section. adapt ive shoot-through circuitry monitors the lgate voltage and determines the upper gate delay time [t pdhu ]. this prevents both the lower and upper mosfets from conducting simultaneously. once this delay period is complete, the upper gate drive begins to rise [t ru ] and the upper mosfet turns on. a falling transition on pwm results in the turn-off of the upper mosfet and the turn-on of the lower mosfet. a short propagation delay [t pdlu ] is encountered before the upper gate begins to fall [t fu ]. again, the adaptive shoot-through circuitry determines the lower gate delay time, t pdhl . the phase voltage and the ugate vo ltage are monitored, and the lower gate is allowed to rise after phase drops below a level or the voltage of ugate to phase reaches a level depending upon the current direction (see next section for details). the lower gate then rises [t rl ], turning on the lower mosfet. advanced adaptive zero shoot-through deadtime control (patent pending) the isl6594d driver incorp orates a unique adaptive deadtime control technique to mi nimize deadtime, resulting in high efficiency from the reduced freewheeling time of the lower mosfets? body-diode conduction, and to prevent the upper and lower mosfets from conducting simultaneously. this is accomplished by ensuring either rising gate turns on its mosfet with minimum and sufficient delay after the other has turned off. during turn-off of the lower mosfet, the phase voltage is monitored until it reaches a -0 .2v/+0.8v trip point within 15ns for a forward/reverse current, at which time the ugate turns on after 10ns propagation delay. an auto-zero comparator is used to correct the r ds(on) drop in the phase voltage preventing from false detection of the -0.2v phase level during r ds(on conduction period. in the case of zero current and/or 15ns phase dete ct expired, the ugate turns on after 10ns propagation delay. during the phase detection, the disturbance of lgate?s fa lling transition on the phase node is blanked out to prevent falsely tripping. once the phase is high, the advanced adaptive shoot-through circuitry monitors the phase and ugate volt ages during a pwm falling edge and the subsequent ugate turn-off. if either the ugate falls to less than 1.75v above the phase or the phase falls to less than +0.8v, the lgate is released to turn on after 10ns propagation delay. three-state pwm input a unique feature of these driver s and other intersil drivers is the addition of a shutdown windo w to the pwm input. if the pwm signal enters and remains within the shutdown window for a set holdoff time, the driver outputs are disabled and both mosfet gates are pulled and held low. the shutdown state is removed when the pwm signal moves outside the shutdown window. otherwise , the pwm rising and falling pwm ugate lgate t fl t pdhu t pdll t rl t tsshd t pdts t pdts 1.18v 7 fn9282.0 march 30, 2006 thresholds outlined in the electrical specifications determine when the lower and upper gates are enabled. this feature helps prevent a ne gative transient on the output voltage when the output is s hut down, eliminating the schottky diode that is used in some systems for protecting the load from reversed output voltage events. in addition, more than 400mv hysteresis also incorporates into the three-state shutdown window to eliminate pwm input oscillations due to the capacitive load seen by the pwm input through the body diode of the controller?s pwm output when the power-up and/or power-down sequence of bias supplies of the driver and pwm controller are required. power-on reset (por) function during initial startup, the vcc voltage rise is monitored. once the rising vcc voltage exceeds 6.4v (typically), operation of the driver is enabled and the pwm input signal takes control of the gate dr ives. if vcc drops below the falling threshold of 5.0v (typica lly), operation of the driver is disabled. pre-por overvoltage protection prior to vcc exceeding its por level, the upper gate is held low and the lower gate is controlled by the overvoltage protection circuits. the phase is connected to the gate of the low side mosfet (lgate), which provides some protection to the microprocessor if the upper mosfet(s) is shorted during startup, normal, or shutdown conditions. for complete protection, the low side mosfet should have a gate threshold well below the maximum voltage rating of the load/microprocessor. internal bootstrap device both drivers feature an intern al bootstrap schottky diode. simply adding an external capacitor across the boot and phase pins completes the boots trap circuit. the bootstrap function is also designed to prevent the bootstrap capacitor from overcharging due to the large negative swing at the trailing-edge of the phase n ode. this reduces voltage stress on the boot to phase pins. the bootstrap capacitor must have a maximum voltage rating above pvcc + 5v and its capacitance value can be chosen from the following equation: where q g1 is the amount of gate charge per upper mosfet at v gs1 gate-source voltage and n q1 is the number of control mosfets. the dv boot_cap term is defined as the allowable droop in the rail of the upper gate drive. as an example, suppose two irlr7821 fets are chosen as the upper mosfets. the gate charge, q g , from the data sheet is 10nc at 4.5v (v gs ) gate-source voltage. then the q gate is calculated to be 53nc for pvcc = 12v. we will assume a 200mv droop in drive voltage over the pwm cycle. we find that a bootstrap capacitan ce of at least 0.267 f is required. gate drive voltage versatility the isl6594d provides the user flexibility in choosing the gate drive voltage for efficiency optimization. the isl6594d ties the upper and lower drive rails together. simply applying a voltage from +4.5v up to 13.2v on pvcc sets both gate drive rail voltages simultaneously, while vcc?s operating range is from +6.8v up to 13.2v. for 5v operation, isl6596/isl6609 is recommended. power dissipation package power dissipation is mainly a function of the switching frequency (f sw ), the output drive impedance, the external gate resistance, and the selected mosfet?s internal gate resistance and total gate charge. calculating the power dissipation in the driv er for a desired application is critical to ensure safe operation. exceeding the maximum allowable power dissipation level will push the ic beyond the maximum recommended operating junction temperature of 125c. the maximum allowable ic power dissipation for the so8 package is approximately 800mw at room temperature, while the power dissipation capacity in the dfn package, with an exposed heat escape pad, is more than 1.5w. the dfn package is more suitable for high frequency applications. see layout considerations paragraph for thermal transfer improvement suggestions. when designing the driver into an applicati on, it is recommended that the following calculation is used to ensure safe operation at the desired frequency for the select ed mosfets. the total gate drive power losses due to the gate charge of mosfets and c boot_cap q gate v boot_cap -------------------------------------- q gate q g1 pvcc ? v gs1 ----------------------------------- - n q1 ? = (eq. 1) 50nc 20nc figure 2. bootstrap capacitance vs boot ripple voltage v boot_cap (v) c boot_cap ( f) 1.6 1.4 1.2 1. 0.8 0.6 0.4 0.2 0.0 0.3 0.0 0.1 0.2 0.4 0.5 0.6 0.9 0.7 0.8 1.0 q gate = 100nc isl6594d
8 fn9282.0 march 30, 2006 the driver?s internal circuitry and their corresponding average driver current can be estima ted with equations 2 and 3, respectively, where the gate charge (q g1 and q g2 ) is defined at a particular gate to source voltage (v gs1 and v gs2 ) in the corresponding mosfet datasheet; i q is the driver?s total quiescent current with no l oad at both drive outputs; n q1 and n q2 are number of upper and lower mosfets, respectively; pvcc is the drive voltage for both upper and lower fets. the i q* vcc product is the quiescent power of the driver without capacitive l oad and is typically 116mw at 300khz and vcc = pvcc = 12v. the total gate drive power losses are dissipated among the resistive components along th e transition path. the drive resistance dissipates a portion of the total gate drive power losses, the rest will be dissipated by the external gate resistors (r g1 and r g2 ) and the internal gate resistors (r gi1 and r gi2 ) of mosfets. figures 3 and 4 show the typical upper and lower gate drives turn-on transition path. the power dissipation on the driver can be roughly estimated as: application information layout considerations the parasitic inductances of the pcb and of the power devices? packaging (both upper and lower mosfets) can cause serious ringing, exceeding absolute maximum rating of the devices. careful layo ut can help minimize such unwanted stress. the following advice is meant to lead to an optimized layout: ? keep decoupling loops (pvcc-gnd and boot-phase) as short as possible. ? minimize trace inductance, especially on low-impedance lines. all power traces (ugate, phase, lgate, gnd, pvcc) should be short and wide, as much as possible. ? minimize the inductance of the phase node. ideally, the source of the upper and the drain of the lower mosfet should be as close as thermally allowable. ? minimize the current loop of the output and input power trains. short the source connection of the lower mosfet to ground as close to the transistor pin as feasible. input capacitors (especially cera mic decoupling) should be placed as close to the drain of upper and source of lower mosfets as possible. in addition, for heat spreading, place copper underneath the ic whether it has an exposed pad or not. the copper area can be extended beyond the bottom area of the ic and/or connected to buried power ground plane(s) with thermal vias. this combination of vias for vertical heat escape, p qg_tot p qg_q1 p qg_q2 i q vcc ? ++ = (eq. 2) p qg_q1 q g1 pvcc 2 ? v gs1 -------------------------------------- - f sw ? n q1 ? = p qg_q2 q g2 pvcc 2 ? v gs2 -------------------------------------- - f sw ? n q2 ? = i dr q g1 pvcc n q1 ? ? v gs1 ----------------------------------------------------- q g2 pvcc n q2 ? ? v gs2 ----------------------------------------------------- + ?? ?? ?? f sw i q + ? = (eq. 3) p dr p dr_up p dr_low i q vcc ? ++ = (eq. 4) p dr_up r hi1 r hi1 r ext1 + -------------------------------------- r lo1 r lo1 r ext1 + ---------------------------------------- + ?? ?? ?? p qg_q1 2 --------------------- ? = p dr_low r hi2 r hi2 r ext2 + -------------------------------------- r lo2 r lo2 r ext2 + ---------------------------------------- + ?? ?? ?? p qg_q2 2 --------------------- ? = r ext1 r g1 r gi1 n q1 ------------- + = r ext2 r g2 r gi2 n q2 ------------- + = figure 3. typical upper-gate drive turn-on path figure 4. typical lower-gate drive turn-on path q1 d s g r gi1 r g1 boot r hi1 c ds c gs c gd r lo1 phase pvcc pvcc q2 d s g r gi2 r g2 r hi2 c ds c gs c gd r lo2 isl6594d
9 fn9282.0 march 30, 2006 extended copper plane, and buried planes for heat spreading allows the ic to achi eve its full thermal potential. upper mosfet self turn -on effects at start-up should the driver have insuffici ent bias voltage applied, its outputs are floating. if the in put bus is energized at a high dv/dt rate while the driver out puts are floating, because of self-coupling via the internal c gd of the mosfet, the ugate could momentarily rise up to a level greater than the threshold voltage of the mosfet. this could potentially turn on the upper switch and result in damaging inrush energy. therefore, if such a situation (when input bus powered up before the bias of t he controller and driver is ready) could conceivably be encountered, it is a common practice to place a resistor (r ugph ) across the gate and source of the upper mosfet to suppress the miller coupling effect. the value of the resistor depends mainly on the input voltage?s rate of rise, the c gd /c gs ratio, as well as the gate-source threshold of the upper mosfet . a higher dv/dt, a lower c ds /c gs ratio, and a lower gate-source threshold upper fet will require a smaller resistor to diminish the effect of the internal capacitive coupling. for most applications, a 5k to 10k resistor is typically suffi cient, not affecting normal performance and efficiency. the coupling effect can be roughly estimated with the following equations, which assume a fixed linear input ramp and neglect the clamping effect of the body diode of the upper drive and the bootstrap capacitor. other parasitic components such as lead inductances and pcb capacitances are also not taken into account. these equations are provided fo r guidance purpose only. therefore, the actual coupling effect should be examined using a very high impedance (10m or greater) probe to ensure a safe design margin. v gs_miller dv dt ------- rc rss 1e v ? ds dv dt ------- rc ? iss ? --------------------------------- - ? ?? ?? ?? ?? ?? ?? ?? = rr ugph r gi + = c rss c gd = c iss c gd c gs + = (eq. 5) figure 5. gate to source resistor to reduce upper mosfet miller coupling vin q upper d s g r gi r ugph boot du c ds c gs c gd dl phase pvcc isl6594d c boot ugate isl6594d
10 fn9282.0 march 30, 2006 isl6594d dual flat no-lead plastic package (dfn) d e a b 0.10 mc e 0.415 c section "c-c" nx (b) (a1) 2x c 0.15 0.15 2x b nx l ref. (nd-1)xe 5 a c (datum b) d2 d2/2 e2 e2/2 top view 7 bottom view 5 6 index area 8 ab nx k 6 index area (datum a) 12 n-1 n nx b 8 nx b nx l 0.200 c a seating plane 0.08 c a3 side view 0.10 c l10.3x3 10 lead dual flat no-lead plastic package symbol millimeters notes min nominal max a 0.80 0.90 1.00 - a1 - - 0.05 - a3 0.20 ref - b 0.18 0.23 0.28 5,8 d 3.00 bsc - d2 1.95 2.00 2.05 7,8 e 3.00 bsc - e2 1.55 1.60 1.65 7,8 e 0.50 bsc - k0.25 - - - l0.30 0.35 0.40 8 n102 nd 5 3 rev. 3 6/04 notes: 1. dimensioning and tolerancing conform to asme y14.5-1994. 2. n is the number of terminals. 3. nd refers to the number of terminals on d. 4. all dimensions are in millimeters. angles are in degrees. 5. dimension b applies to the meta llized terminal and is measured between 0.15mm and 0.30mm from the terminal tip. 6. the configuration of the pin #1 identifier is optional, but must be located within the zone indicated. the pin #1 identifier may be either a mold or mark feature. 7. dimensions d2 and e2 are fo r the exposed pads which provide improved electrical and thermal performance. 8. nominal dimensions are prov ided to assist with pcb land pattern design efforts, see intersil technical brief tb389. for odd terminal/side c l e terminal tip l c c
11 all intersil u.s. products are manufactured, asse mbled and tested utilizing iso9000 quality systems. intersil corporation?s quality certifications ca n be viewed at www.intersil.com/design/quality intersil products are sold by description only. intersil corpor ation reserves the right to make changes in circuit design, soft ware and/or specifications at any time without notice. accordingly, the reader is cautioned to verify that data sheets are current before placing orders. information furnishe d by intersil is believed to be accurate and reliable. however, no responsibility is assumed by intersil or its subsidiaries for its use; nor for any infringements of paten ts or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of intersil or its subsidiari es. for information regarding intersil corporation and its products, see www.intersil.com fn9282.0 march 30, 2006 isl6594d small outline plast ic packages (soic) index area e d n 123 -b- 0.25(0.010) c a m bs e -a- l b m -c- a1 a seating plane 0.10(0.004) h x 45 c h 0.25(0.010) b m m notes: 1. symbols are defined in the ?mo series symbol list? in section 2.2 of publication number 95. 2. dimensioning and tolerancing per ansi y14.5m - 1982. 3. dimension ?d? does not include mold flash, protrusions or gate burrs. mold flash, protrusion and gate burrs shall not exceed 0.15mm (0.006 inch) per side. 4. dimension ?e? does not include in terlead flash or protrusions. inter- lead flash and protrusions shall not exceed 0.25mm (0.010 inch) per side. 5. the chamfer on the body is optional. if it is not present, a visual index feature must be located within the crosshatched area. 6. ?l? is the length of terminal for soldering to a substrate. 7. ?n? is the number of terminal positions. 8. terminal numbers are shown for reference only. 9. the lead width ?b?, as measured 0.36mm (0.014 inch) or greater above the seating plane, shall not exceed a maximum value of 0.61mm (0.024 inch). 10. controlling dimension: millimete r. converted inch dimensions are not necessarily exact. m8.15 (jedec ms-012-aa issue c) 8 lead narrow body small outline plastic package symbol inches millimeters notes min max min max a 0.0532 0.0688 1.35 1.75 - a1 0.0040 0.0098 0.10 0.25 - b 0.013 0.020 0.33 0.51 9 c 0.0075 0.0098 0.19 0.25 - d 0.1890 0.1968 4.80 5.00 3 e 0.1497 0.1574 3.80 4.00 4 e 0.050 bsc 1.27 bsc - h 0.2284 0.2440 5.80 6.20 - h 0.0099 0.0196 0.25 0.50 5 l 0.016 0.050 0.40 1.27 6 n8 87 0 8 0 8 - rev. 1 6/05
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